Interface with variable data rate

ABSTRACT

A device includes a transmitter coupled to a node, where the node is to couple to a wired link. The transmitter has a plurality of modes of operation including a calibration mode in which a range of communication data rates over the wired link is determined in accordance with a voltage margin corresponding to the wired link at a predetermined error rate. The range of communication data rates includes a maximum data rate, which can be a non-integer multiple of an initial data rate.

RELATED APPLICATIONS

This is a continuation of U.S. patent application Ser. No. 15/393,234,filed Dec. 28, 2016, which is a continuation of U.S. patent applicationSer. No. 14/931,652, filed Nov. 3, 2015, now U.S. Pat. No. 9,569,396,which is a continuation of U.S. patent application Ser. No. 14/507,743,filed Oct. 6, 2014, now U.S. Pat. No. 9,178,647, which is a continuationof U.S. patent application Ser. No. 13/633,076, filed Oct. 1, 2012, nowU.S. Pat. No. 8,855,217, which is a continuation of U.S. patentapplication Ser. No. 12/518,781, filed Dec. 21, 2009, now U.S. Pat. No.8,279,948, which is a United States National Stage Application filedunder 35 U.S.C. § 371 of PCT Patent Application Serial No.PCT/US2007/087027, filed on Dec. 10, 2007, which claims the benefit ofand priority to U.S. Provisional Patent Application Ser. No. 60/869,896filed on Dec. 13, 2006 and U.S. Provisional Patent Application Ser. No.60/869,895 filed on Dec. 13, 2006, all of which are hereby incorporatedby reference in their entireties.

FIELD

The subject matter disclosed herein relates generally to circuits foruse in integrated circuits, and in particular, to circuits andassociated methods for determining a range of data rates of an interfacethat is consistent with a specified data error rate.

BACKGROUND

Many devices and systems include circuits that are designed based ontarget performance characteristics. Unfortunately, these circuits maynot always meet these targets. For example, effects such as processvariations during manufacturing, variations in a power supply voltage,variations in temperature, or even aging of a component may result in adistribution of performance characteristics, some of which may fallbelow the targets.

In the case of input/output (I/O) interfaces, a failure to achieve atarget data rate often results in a complete failure of the device orsystem that includes the interface. An inability to adapt the data rateor to adjust one or more circuit parameters to achieve a desired datarate may, therefore, have consequences for overall yield, cost, lifespanand the reliability of the devices or systems.

There is a need, therefore, for improved I/O interfaces whose data ratemay be adapted or adjusted without the aforementioned problems.

BRIEF DESCRIPTION OF THE DRAWINGS

For a better understanding, reference should be made to the followingdetailed description taken in conjunction with the accompanyingdrawings, in which:

FIG. 1 is a block diagram illustrating an embodiment of a system havinga plurality of devices coupled to a controller.

FIG. 2A is a block diagram illustrating an embodiment of a system havingtwo devices interconnected by a wired link.

FIG. 2B is a block diagram illustrating another embodiment of a systemhaving two devices interconnected by a wired link.

FIG. 3A is a block diagram illustrating an embodiment of a device havinga receiver.

FIG. 3B is a block diagram illustrating an embodiment of a receiver.

FIG. 4A illustrates an eye pattern.

FIG. 4B illustrates a plurality of error rates and associated offsetvoltages with respect to an eye pattern.

FIG. 5 illustrates an embodiment of a relationship between error rateand a voltage or timing margin.

FIG. 6A is a flow diagram illustrating an embodiment of a method fordetermining a device's maximum data rate that is consistent with aspecified data error rate.

FIG. 6B is a flow diagram illustrating an embodiment of a method fordetermining a voltage margin that corresponds to a specified data errorrate.

FIG. 7 is a block diagram illustrating an embodiment of a system.

FIG. 8 is a block diagram illustrating an embodiment of a datastructure.

FIG. 9 is a block diagram illustrating an embodiment of a datastructure.

Like reference numerals refer to corresponding parts throughout thedrawings.

DETAILED DESCRIPTION OF EMBODIMENTS

Embodiments of a device are described. The device includes a transmittercoupled to a node, where the node is to couple to a wired link. Thetransmitter has a plurality of modes of operation including acalibration mode in which a maximum data rate of communication ofinformation over the wired link is determined in accordance with avoltage margin corresponding to the wired link at a predetermined errorrate (e.g., a maximum acceptable error rate). The maximum data rate is anon-integer multiple of a data clock frequency.

A method for determining the maximum data rate of communication over thewired link in a calibration mode of operation includes determining avoltage margin at a receive circuit while receiving data transmittedover the wired link at an initial data rate. The voltage margin isdetermined iteratively at a sequence of gradually increasing data ratesuntil a respective voltage margin corresponds to an error rate that isgreater than a predetermined error rate. The data rate increment betweeniterations is a non-integer multiple of the initial data rate. Themaximum data rate can be a non-integer multiple of an initial data rate.

In some embodiments, the maximum data rate is further determined inaccordance with a timing margin corresponding to the wired link at thepredetermined error rate.

In some embodiments, the transmitter includes a fractional-N phaselocked loop. In some embodiments, the device includes a microprocessor.

The device may optionally include control logic to determine the maximumdata rate using an iterative process in which the data rate is increaseduntil a measured voltage margin corresponds to an error rate that isgreater than the predetermined error rate. Optionally, the control logicmay also be configured to modify a supply voltage and/or a voltage swingof a transmit circuit in the transmitter if the maximum data rate isless than a target data rate.

Optionally, the transmitter may report determined values of the datarate and corresponding voltage margins to a system that includes thedevice. Optionally, the transmitter may include a loop back path betweena transmit circuit and a calibration circuit during the calibrationmode.

The present invention may be implemented in a system that includes afirst device having a transmit circuit, a second device that includes areceive circuit, and a wired link coupled to transmit and receivecircuits.

Reference will now be made in detail to embodiments, examples of whichare illustrated in the accompanying drawings. In the following detaileddescription, numerous specific details are set forth in order to providea thorough understanding of the subject matter presented herein.However, it will be apparent to one of ordinary skill in the art thatthe subject matter may be practiced without these specific details. Inother instances, well-known methods, procedures, components, andcircuits have not been described in detail so as not to unnecessarilyobscure aspects of the embodiments.

Circuits, such as interfaces, and related methods are described. Amaximum data rate of communication of information over a wired linkcoupled to a respective circuit may be determined in an iterativeprocess by control logic. The maximum data rate may correspond to apredetermined error rate (such as a bit error rate or BER), and may bedetermined using a voltage margin and/or a timing margin. The maximumdata rate may be a non-integer multiple (e.g., a value between one andtwo) of an initial data rate.

In some embodiments, a voltage margin of the circuit is predicted bydetermining voltage margins at a first error rate and at a second errorrate. For example, offset voltages may be applied to a receive circuitin the circuit, thereby changing the threshold of the receive circuit.For a respective error rate, the voltage margin corresponds to theoffset voltage that degrades the error rate sufficiently that itapproximately equals the respective error rate. Two or more of thesevoltage margins may be used to determine a noise metric, such as an rmsnoise. In conjunction with a measured or predetermined relationshipbetween a signal-to-noise ratio and the error rate, the rms noise andthe first error rate may be used to predict the voltage margin at athird error rate. Typically, the first and second error rates are largerthan the third error rate, perhaps by several orders of magnitude. Inthis way, measurements may be performed in a reasonable amount of timeand the results of these measurements may be used to predict performanceof the circuit at lower error rates.

By determining a range of data rates between an initial data rate and amaximum data rate of a link (corresponding to a specified error rate),the circuit may be adjusted and/or adapted. In some embodiments, asupply voltage and/or a voltage swing of a transmit circuit is adjustedif the maximum data rate is different than a target data rate. Forexample, the supply voltage may be increased if the maximum data rate isless than the target data rate, or the supply voltage may be decreasedif the maximum data rate is more than the target data rate. The abilityto determine a range of data rates of the link for a specified errorrate, and/or to adjust the circuit based on the maximum data rate mayoffer improved yield, improved performance (such as data rate and/orpower management), and/or reduced cost. In some embodiments, the supplyvoltage for the entire interface (e.g., including a PLL as well as thetransmit circuit, and optionally additional interface circuitry as well)is adjusted in accordance with the criteria stated above.

The circuit may include a memory controller and/or a memory device. Thememory device may include a memory core that utilizes solid-statememory, semiconductor memory, organic memory and/or another memorymaterial, including volatile and/or non-volatile memory. The memorydevice may include dynamic random access memory (DRAM), static randomaccess memory (SRAM) and/or electrically erasable programmable read-onlymemory (EEPROM). The circuit may be included in one or more componentsin a memory system, such as a memory controller and/or one or morememory devices. The one or more memory devices may be embedded in one ormore memory modules. The memory controller and the one or more memorydevices may be on a common or same circuit board. The circuit may beincluded in one or more components in other systems, such as those thatinclude logic chips, including a serializer/deserializer, PCI Expressand/or other high-speed interfaces (such as serial links) orinput/output links. The circuit may be included in a microprocessorand/or a motherboard for a computer.

Attention is now directed towards embodiments that address thedifficulties associated with the existing interface circuits describedpreviously. FIG. 1 is a block diagram illustrating an embodiment of asystem 100. The system 100 includes at least one controller 110 and oneor more devices 112, such as one or more memory devices. While FIG. 1illustrates the system 100 having one controller 110 and three devices112, other embodiments may have additional controllers and fewer or moredevices 112. Also, while the system 100 illustrates the controller 110coupled to multiple devices 112, in other embodiments two or morecontrollers may be coupled to one another. The controller 110 mayinclude control logic 120-1 and an I/O interface 118-1. Optionally, oneor more of the devices 112 may include control logic 120 and at leastone of interfaces 118. In some embodiments, some of the devices 112 maynot have control logic 120 and/or the interfaces 118. In someembodiments, the controller 110 and/or one or more of the devices 112may include a plurality of the interfaces 118, which may optionallyshare control logic 120. In embodiments where the devices 112 are memorydevices, two or more of the devices, such as devices 112-1 and 112-2,may be configured as a memory bank 116.

The controller 110 and the devices 112 are connected by one or morelinks 114. While the system 100 illustrates three links 114, otherembodiments may have fewer or more links 114. In some embodiments, thelinks 114 correspond to wired communication links. The links 114 may beused for bi-directional and/or uni-directional communications betweenthe controller 110 and one or more of the devices 112. Bi-directionalcommunication may be simultaneous. In some embodiments, one or more ofthe links 114 and corresponding transmit circuits (illustrated in FIG.3A) and/or receive circuits (illustrated in FIGS. 3A and 3B) may bedynamically configured, for example, by the control logic 120 of acontroller 110, for bi-directional and/or unidirectional communication.

One or more of the control logic 120 circuits may be used to determinethe maximum data rate of communication of information over at least oneof the links 114. The control logic 120 circuits may allow improvedperformance (increased data rates and/or reduced power consumption), aswell as lower cost of the system 100.

FIG. 2A is a block diagram illustrating an embodiment of a system 200.The system 200 includes a device 210-1 coupled to device 210-2 via awired link 224. Each of the devices 210 includes at least onetransceiver 214 to transmit and receive data on the wired link 224 at avariable and/or an adjustable data rate. Note that in the discussionthat follows, data rate is taken to be a physical transmissionfrequency, as opposed to an effective data rate such as that used insystems where dropped packets are retransmitted. The transceivers 214may transmit and/or receive the data using clock signals provided by oneof the phase locked loops (PLL) 216. The phase locked loops 216 maygenerate the clock signals using primary or reference clock signals 218.In an exemplary embodiment, the phase locked loops 216 includefractional-N phase locked loops and/or sigma-delta phase locked loops.Such phase locked loops allow the data rate to be a non-integer multipleof the reference clock frequency. Each of the transceivers 214 is alsocoupled to one of the power supplies 220, which provides one or moresupply voltages.

At least one of the devices 210 includes control logic 212. One or moreof the control logic 212 circuits may be used to determine a maximumdata rate of communication of information over a communication channelthat includes the wired link 224 and one or more of the transceivers 214in a calibration mode of operation. The communication channel mayinclude a physical layer, such as the wired link 224, and a data layerin protocol stacks in one or more of the devices 210. In someembodiments, the maximum data rate is determined based on communicationover the wired link 224. For example, data is transmitted by transceiver214-1 at a data rate over the wired link 224, and this data is receivedby transceiver 214-2 in the device 210-2. The data may then betransmitted back to device 210-1 where an error rate is determined orinferred (for example, based on a voltage or timing margin).Alternatively, the error rate is determined or inferred in the device210-2, and the results may be communicated back to device 210-1.

In other embodiments, during the calibration mode of operation one ofoptional loop backs 222 may couple a transmit circuit to a receivecircuit in a respective transceiver, such as transceiver 214-1. Notethat the loop backs 222 may allow device-related issues in acommunication channel to be isolated. The receive circuit may include acalibration circuit that is used to determine a performance metric, suchas the error rate, voltage margin and/or timing margin. In this way, therespective transceiver may be used to determine, either directly (bymeasurement) or indirectly (using the voltage and/or timing margins),the error rate corresponding to the data rate. In some embodiments,characteristics of the optional loop backs 222 (such as an impedanceand/or a length) are selected to mimic the characteristics of the wiredlink 224.

One or more of the control logic 212 circuits may determine the maximumdata rate of communication over the wired link 224 using anauto-negotiation procedure. An initial or safe data rate may be used,such as 80% of a target data rate. The performance of the wired link224, such as a voltage and/or timing margin that corresponds to apredetermined error rate, may be determined. (This process is describedfurther below with reference to FIGS. 4, 5 and 7).

After determining the performance, the data rate is increased (e.g., byincreasing the PLL output frequency by a fraction of the initial PLLoutput frequency) and the process is repeated iteratively until thewired link 224 fails, i.e., the performance is insufficient. Forexample, the wired link 224 is deemed to have failed when the determinedvoltage margin and/or timing margin correspond to an error rate that islarger than the predetermined error rate. When this occurs, one or moreof the control logic 212 circuits determines the maximum data rate asthe last or highest data rate that had acceptable performance. In anexemplary embodiment, the maximum data rate is less than twice theinitial data rate in the auto-negotiation procedure. In anotherexemplary embodiment, the maximum data rate is up to 1.5 times theinitial data rate.

One or more of the control logic 212 circuits may report the maximumdata rate, as well as the measured voltage and/or timing margin as afunction of the data rate, to a host in the system 200. In someembodiments, the host is one or more of the control logic 212 circuits,such as control logic in a memory controller. In some embodiments, thehost is a microprocessor. The host may use this information to adaptand/or adjust one or more of the transceivers 214. For example, ifperformance is important, a maximum data rate of one or more of thetransceivers 214 may be selected by setting one or more register valuesin the corresponding phase locked loops 216. Alternatively, if power isa constraint, a data rate lower than the maximum data rate may be used.In some embodiments, the control logic enables continued operation of atransmitter even if the maximum data rate is less than a target datarate. For example, continued operation may be permitted so long as themaximum data rate is within a predefined percentage (e.g., 1%, 2% or 5%)of the target data rate.

In other embodiments, a supply voltage and/or a transmit voltage swingof one or more of the transceivers 214 may be adjusted. The former isillustrated by the dashed lines in FIG. 2A. For example, if thedetermined maximum data rate is greater than the target data rate, thesupply voltage and/or the voltage swing may be reduced. Alternatively,if the determined maximum data rate is less than the target data rate,the supply voltage and/or the voltage swing may be increased. Theadjustment of the supply voltage and/or the voltage swing may be basedon a known relationship between the maximum data rate and the voltageswing or the supply voltage (for example, the maximum data rate isproportional to the square root of the supply voltage), or such arelationship(s) may be measured.

Using this approach, the host may adjust and/or adapt performance inaccordance with constraints on the data rate and/or power consumption.For example, since many communication channels are over designed inorder to meet worst-case conditions, non-worst-case channels may beoperated with a lower supply voltage and/or voltage swing.Alternatively, data rates below the maximum may be used, therebyimproving a communication channel that is failing. Furthermore, systemsand devices, such as the system 200 and the devices 210, may be binned(e.g., assigned to predefined device grades) based on their maximum datarates. In other embodiments, the auto-negotiation may improveconvergence in communication channels that use decision feedbackequalization (DFE), may enable advanced system diagnostics, and/or mayallow a frequency profile of the communication channel to be determined.In another embodiment, the host may determine that the maximum data rateis close enough to the target data rate (or another system constraint)and choose to do nothing, i.e., to make no changes to the system 200 ata given time.

The auto-negotiation procedure may be performed once or multiple times.For example, the auto-negotiation procedure may be performed when thesystem 200 is manufactured, at boot time (when the system 200 is poweredon), or dynamically. Dynamic adjustment may occur after a predeterminedtime interval or as needed, such as when the performance of thecommunication channel is insufficient.

In an illustrative embodiment, the auto-negotiation procedure determinesthe maximum data rate in the range of 8-15 Gbps about a 10 Gbps target,using data rate increments of 5%. In another illustrative embodiment,the auto-negotiation procedure determines the maximum data rate in therange of 8-12 Gbps using 100 Mbps increments. In yet anotherillustrative embodiment, a PCI Express interface in a portablemotherboard fails (i.e., has too large of an error rate) at a data rate2.5 Gbps. Based on a determined maximum data rate, the motherboard maybe used at 2.25 Gbps or may be used at 2.5 Gbps in conjunction with ahigher supply voltage or voltage swing.

In some embodiments, the system 200 may include fewer or additionalcomponents, logical positions of one or more components in the system200 may be changed, and two or more of the components may be combinedand/or shared. For example, in some embodiments clock signals 218 are acommon clock signal. Or in some embodiments only one of the devices 210includes control logic. This is illustrated in embodiment 250 in FIG.2B.

FIG. 3A is a block diagram illustrating an embodiment 300 of a device310. The device 310 receives a clock signal 312, such a reference clocksignal. A frequency synthesizer 314, which may include a fractional-Nphase locked loop, generates clock signals that determine transmit timesof transmit circuits 324 and sampling times of receive circuits 316. Thetransmit circuits 324 output baseband signals having a voltage swing(not shown) that correspond to data signals 326 using supply voltages328. The receive circuits 316 output data signals corresponding toreceived signals 318 using supply voltages 320. The supply voltages 320and 328 may be provided by a power supply 322. Furthermore, the receivecircuits 316 and the transmit circuits 324 may be included in aninterface circuit.

Offset voltages 330 may be applied to the receive circuits 316 to adjustone or more thresholds of the receive circuits 330. For receive circuits316 that receive a baseband signal that includes binary data, there isone threshold per receive circuit, while receive circuits that receivesymbols that represent more than one bit per symbol (e.g., symbolstransmitted using 4-level pulse amplitude modulation) there may be twoor more thresholds. This adjustment capability may be used to trimvariations in the thresholds and/or to determine a voltage margin of acommunication channel. Determining such a voltage margin is discussedfurther below with reference to FIGS. 3B, 4A and 4B.

The device 310 may include control logic or a command buffer 308. Inembodiments with a command buffer, command instructions from a host oranother device that includes control logic may be received by such acommand buffer. The control logic or command buffer 308 may providesignals that adjust the data rate of one or more of the transmitcircuits 324 (for example, by changing a register in the frequencysynthesizer 314), the voltage swing of one or more of the transmitcircuits 324, and/or one or more of the supply voltages 320 and 328. Forexample, one or more of the supply voltages 320 and 328 may be changedby modifying a setting in the power supply 322.

FIG. 3B is a block diagram illustrating an embodiment of a receiver 350.In contrast with the receive circuits 316 in the device 310 (FIG. 3A),the receive circuits 360 are differential, i.e., they each areconfigured to receive baseband differential signals 362. The receivecircuits 360 using supply voltages 320. In this embodiment, the receiver350 includes two receive circuits 360. Receive circuit 360-2 receivesthe differential signals 362 and outputs data signals. A threshold ofreceive circuit 360-1, however, may be adjusted using offset voltage330-2. If the offset voltage 330-2 exceeds a voltage margin of acommunication channel, data signals output by the receive circuit 360-1may differ from those output by receive circuit 360-2. The data signalsoutput by the receive circuits 360-1 and 360-2 are compared using XORcircuit 364. By sweeping the offset voltage 330-2 and detectingdifferences between the outputs from the receive circuits 360, thereceiver 350 may be used to determine the voltage margin at a givenerror rate. This is discussed further below with reference to FIGS. 4Aand 4B.

In some embodiments, the device 310 and/or the receiver 350 may includefewer or additional components, logical positions of one or morecomponents may be changed, and two or more of the components may becombined and/or shared.

FIG. 4A illustrates an eye pattern 400. The eye pattern 400 correspondsto a pattern of baseband signals received by a receive circuit, such asone of the receive circuits 316 (FIG. 3A), via one of the links 114(FIG. 1). By adjusting the phase of one or more clock signals that aregenerated by the frequency synthesizer 314 (FIG. 3A), such as the clocksignal used to determine a transmit time for one of the transmitcircuits 324 (FIG. 3A) and/or the clock signal that determines asampling time of one of the receive circuits 316 (FIG. 3A), the phase ofa received baseband signal may be swept across the eye pattern 400.Typically, only a subset of the phases will result in an acceptable BER.Phases that yield an acceptable BER may be labeled as passing (P) andphases that yield an unacceptable BER may be labeled as failing (F). Therange of allowed phases (i.e., phases with acceptable BER) typicallyincludes a central portion of the eye pattern 400. The range of allowedphases has a left-hand or fail-pass (FP) boundary 410-1 and a right-handor pass-fail (PF) boundary 410-2 that define a timing margin.

Furthermore, as discussed above with reference to FIG. 3B, by adjustingan offset voltage applied to at least one of the receive circuits 360(FIG. 3B) or 316 (FIG. 3A), a threshold voltage may be swept across theeye pattern 400 in a vertical direction, in a sequence of steps.Sweeping the threshold voltage by varying the offset voltage across arange of offset voltages (e.g., in a sequence of steps) is sometimesreferred to as a voltage schmoo. Once again, typically only a subset ofthe threshold voltages will result in an acceptable BER. Voltages thatyield an acceptable BER may be labeled as passing (P) and voltages thatyield an unacceptable BER may be labeled as failing (F). The range ofallowed voltages (i.e., voltages with acceptable BER) typically includesa central portion of the eye pattern 400. The range of allowed voltageshas an upper or fail-pass (FP) boundary 412-1 and a lower or pass-fail(PF) boundary 412-2 that define a voltage margin. Note that in somecircuits or systems, the voltage and the timing margins are related toone another, for example, linearly.

Communication channels are usually designed to have a low error rateunder nominal operating conditions. As a consequence, it is oftendifficult to measure these error rates directly because error events areinfrequent (e.g., error rates under nominal operating conditions may beless than 10⁻¹²). Thus, data error rate (e.g., bit error rate)measurements are often time consuming. In some embodiments, offsetvoltages may be used to degrade the performance of the communicationchannel, i.e., to increase the error rate. Using measured offsetvoltages at different error rates, predictions of offset voltages and/orvoltage margins at other error rates may be determined. Such predictionsmay be based on a known relationship between the error rate and thesignal-to-noise ratio of the communication channel. In some embodiments,this relationship is measured and stored as a calibration curve for usein such analysis.

A technique for predicting voltage margin as function of the data errorrate, or vice-versa, is illustrated in FIG. 4B, which shows an eyepattern 450 and a set of offset voltages 462. A first offset voltage462-1 corresponding to a first error rate 464-1 is determined, andsecond offset voltage 462-2 corresponding to a second error rate 464-2is determined. Furthermore, a noise metric, such as an rms noise, isdetermined using the first offset voltage and the second offset voltage,as will be described in more detail below. After the noise metric hasbeen determined, a third offset voltage 462-3 corresponding to a thirderror rate 464-3 is predicted. For example, the third offset voltage462-3 may correspond to a very low error rate (e.g., 10⁻¹² or 10⁻¹³)that would otherwise be very time consuming to directly measure.

The noise metric and the prediction of the third offset voltage 462-3 isbased on an established relationship between the error rate and thesignal-to-noise ratio. For some systems or circuits, the relationshipbetween the error rate and the signal-to-noise ratio is

$\begin{matrix}{{{E\; R} = {0.5\mspace{14mu}{{erfc}( \frac{V_{SNR}}{\sqrt{2}} )}}},} & (1)\end{matrix}$where ER is the error rate, erfc( ) is a complementary error function,and V_(SNR) is the voltage ratio of signal to RMS noise (and thusV_(SNR) is a signal-to-noise ratio). In other embodiments, therelationship may be based on colored noise and/or one or more dominanterror events, as is known in the art. The voltage signal-to-noise ratioV_(SNR) may be defined as

$V_{SNR} = \frac{{signal}\mspace{14mu}{voltage}}{{rms}\mspace{14mu}{noise}\mspace{14mu}{voltage}}$The complementary error function erfc(z), used in Equation 1, istypically defined as

${{erfc}(z)} = {\frac{2}{\sqrt{\pi}}{\int_{z}^{\infty}{e^{- t^{2}}\ {dt}}}}$although other definitions may be used in other embodiments.

In some embodiments, the third offset voltage is determined inaccordance with the first and second voltages and the noise metric. Forexample, a noise metric N may be determined by the first and secondoffset voltages in accordance with a function of the form:N=(V1−V2)/βwhere V1 is the first offset voltage, corresponding to the higher of thefirst and second error rates (e.g., 10⁻³), V2 is the second offsetvoltage, corresponding to the lower of the first and second error rates(e.g., 10⁻⁶), and β is a coefficient determined in accordance with thefirst and second error rates. In some embodiments, a ratio of the firsterror rate to the second error rate is at least 100. In an exemplaryembodiment, the first error rate 464-1 is 10⁻³, the second error rate464-2 is 10⁻⁶, and the rms noise N (over an effective bandwidth of thecommunication channel) equals approximately

$\begin{matrix}{{N = \frac{{V\; 1} - {V\; 2}}{1.7}},} & (2)\end{matrix}$If a single measurement during a voltage schmoo takes 1 ms, at a datarate of 10 Gbps each measurement corresponds to 10⁷ bits. Receiving 10⁷bits is sufficient to measure an error rate as low as 10⁻⁶, which wouldproduce about 10 errors in 10⁷ bits. Further, if a binary search is usedto determine a respective offset voltage, the full range of the voltageswing is 200 mV, and the voltage schmoo resolution is 2 mV, determiningthe respective offset voltage will take approximately 7 ms.

Once the rms noise N has been determined, the third offset voltage 462-3corresponding to the target error rate (e.g., the third error rate464-3) may be predicted by a function of the form:V3=V2−αNwhere V2 and N are as defined above and a is a coefficient determined inaccordance with the target error rate and the second error rate. Forexample, by taking the difference of the logarithm of Equation 1 for thesecond error rate 464-2 of 10⁻⁶ and the third error rate 464-3 of 10⁻¹²,the third offset voltage 464-3 is predicted to be approximatelyV2−2.3N,  (3)where N is the rms noise. The coefficient in Equation 3, above, is afunction of the second and third error rates, and therefore thecoefficient will have a value different from 2.3 if the second and thirderror rates differ from the second and third error rates (i.e., 10⁻⁶ and10⁻¹²) used in this example.

In another embodiment, the analysis may be performed using both boundedand random (or pseudo-random) noise. In particular, measurement of theV₁ and V₂ offset voltages may performed at two data error rates (forexample, 10⁻³ and 10⁻⁶, respectively) using a data pattern that has afundamental frequency and a minimum amount of bounded noise. Forexample, if a periodic signal such as a clock signal is used as the datasignal, the fundamental frequency of the data pattern is the clockfrequency. In a communication channel where inter-symbol interference(ISI) is associated with reflections and dispersion in the channel, sucha pattern may have reduced ISI. From these measurements, the rms noisemetric N is determined in accordance with the methodology explainedabove (e.g., using Equation 2, if the first and second error rates are10⁻³ and 10⁻⁶, respectively).

Next, measurement of another offset voltage V4 at the second error ratemay be performed using a pseudo-random pattern, such as a pseudo-randomsequence. Such a pattern may be a worst case pattern that has themaximum bounded noise. From the offset voltage measurement V4 at thiserror rate, the offset voltages V3 at other target error rates may bepredicted, for example, using Equation 4:V3=V4−αN,  (4)where N is the rms noise metric that was previously determined using,for example, a periodic signal, and α is a coefficient whose value isdetermined in accordance with the second error rate and the target errorrate. As noted above, α in Equation 4 is approximately 2.3 when thesecond error rate and the target error rates are 10⁻⁶ and 10⁻¹²,respectively.

As discussed previously, using measurements and/or equations arelationship 500 (illustrated in FIG. 5) between error rate 512 andvoltage or timing margin 510 may be determined. This relationship 500may be used to predict voltage or timing margin at other values of theerror rate 512. Alternatively, the relationship 500 may be used topredict the error rate based on a measured voltage or timing margin at agiven data rate. As such, the relationship 500 may be used during anauto-negotiation procedure. In some embodiments, therefore, aclose-formed expression or a look-up table that includes datarepresenting the relationship 500 may be stored in the controller 110(FIG. 1) and/or one of the devices 112 (FIG. 1). In other embodiments,this information may be stored in a host that includes the controller110 (FIG. 1) and/or one of the devices 112 (FIG. 1).

It is noted that when the predicted offset voltage V3 for a target errorrate is negative, this means that target error rate cannot be achieved(i.e., cannot be achieved using the circuitry on which measurements weretaken).

We now discuss embodiments of processes for determining the maximum datarate and for predicting voltage margin. FIG. 6A is a flow diagramillustrating an embodiment of a method 600 for determining a data rate.The method 600 may be implemented by the control logic (212, FIG. 2A or308, FIG. 3A) of the device in which receive circuit is located and/orthe control logic of the device in which a corresponding transmitcircuit is located. In some embodiments, the control logic of the devicecontaining the receive circuit and/or the device containing the transmitcircuit includes a processor that executes a set of instructions so asto implement the method 600 and/or the method 650 discussed below withreference to FIG. 6B. Alternately, the control logic may be implementedusing one or more state machines to perform the method 600 and/or themethod 650.

In accordance with the method, data is transmitted at a data rate over awired link (610). A voltage and/or a timing margin corresponding to thewired link are determined (612). An error rate corresponding to thevoltage and/or the timing margin are optionally determined (614). If ametric, such as an error rate that is inferred based on the voltageand/or the timing margin, is less than a threshold (616), the data rateis increased (618) and operations 610, 612 and 614 are repeated. If themetric is greater than the threshold (616), a supply voltage and/or avoltage swing are optionally modified in accordance with a determinedmaximum data rate of the wired link (620). For example, the supplyvoltage and/or voltage swing of the received data signal may beincreased so as to decrease the error rate. In some embodiments, thecontinued operation of a transmitter is enabled even if the maximum datarate is less than a target data rate. For example, continued operationmay be permitted so long as the maximum data rate is within a predefinedpercentage (e.g., 1%, 2% or 5%) of the target data rate. In someembodiments, there may be fewer or additional operations, an order ofthe operations may be rearranged and/or two or more operations may becombined.

FIG. 6B is a flow diagram illustrating an embodiment of a method 650 fordetermining a voltage margin. A first offset voltage of a receivecircuit is determined, where the first offset voltage corresponds to afirst error rate (660). A second offset voltage of the receive circuitis determined, where the second offset voltage corresponds to a seconderror rate (662). A noise metric is determined in accordance with thefirst offset voltage and the second offset voltage (664). A third offsetvoltage of the receive circuit is predicted in accordance with the noisemetric and the first offset voltage, where the third offset voltagecorresponds to a third error rate (666). A specific example of thismethod was described above with reference to FIG. 4B. In someembodiments of the method, there may be fewer or additional operations,an order of the operations may be rearranged and/or two or moreoperations may be combined.

Devices and circuits described herein can be implemented using computeraided design tools available in the art, and embodied by computerreadable files containing software descriptions of such circuits, atbehavioral, register transfer, logic component, transistor and layoutgeometry level descriptions stored on storage media or communicated bycarrier waves. Data formats in which such descriptions can beimplemented include, but are not limited to, formats supportingbehavioral languages like C, formats supporting register transfer levelRTL languages like Verilog and VHDL, and formats supporting geometrydescription languages like GDSII, GDSIII, GDSIV, CIF, MEBES and othersuitable formats and languages. Data transfers of such files on machinereadable media including carrier waves can be done electronically overthe diverse media on the Internet or through email, for example.Physical files can be implemented on machine readable media such as 4 mmmagnetic tape, 8 mm magnetic tape, 3½ inch floppy media, CDs, DVDs andso on.

FIG. 7 is a block diagram illustrating an embodiment of a system 700 forstoring computer readable files containing software descriptions of thecircuits. The system 700 may include at least one data processor orcentral processing unit (CPU) 710, memory 714 and one or more signallines or communication busses 712 for coupling these components to oneanother. Memory 714 may include high-speed random access memory and/ornon-volatile memory, such as one or more magnetic disk storage devices.Memory 714 may store a circuit compiler 716 and circuit descriptions718. Circuit descriptions 718 may include circuit descriptions for thecircuits, or a subset of the circuits discussed above with respect toFIGS. 1-3. In particular, circuit descriptions 718 may include circuitdescriptions of one or more transmit circuits or transmitters 720, oneor more receive circuits or receivers 722, one or more control logiccircuits 724, one or more frequency synthesizers 726, one or more phaselocked loops 728, one or more voltage generators 730, one or more powersupplies 732, one or more voltage margin circuits 734, one or moretiming margin circuits 736, and/or one or more bit error ratemeasurement circuits 738.

We now discuss data structures that may used to perform the method fordetermining a maximum data rate. FIG. 8 is a block diagram illustratingan embodiment of a data structure 800. The data structure 800 includesmultiple entries 810. A respective entry, such as entry 810-2, mayinclude a voltage margin value and/or timing margin value 812-2 and acorresponding data rate 814-2. The entries 810 in the data structure 800may be determined using the auto-negotiation procedure describedpreviously.

FIG. 9 is a block diagram illustrating an embodiment of a data structure900. The data structure 900 includes multiple entries 910. A respectiveentry, such as entry 910-2, may include a voltage margin value and/ortiming margin value 912-2, and a corresponding error rate 914-2. Thedata structure may correspond to the relationship 500 (FIG. 5), whichmay be used to predict the voltage or timing margin at different valuesof the error rate. The data structures 800 and/or 900 may be reported toa host, where they may be used to determine a data rate, a supplyvoltage, and/or a voltage swing based on one or more system constraints,such as performance or power consumption.

The foregoing descriptions of specific embodiments of the presentinvention are presented for purposes of illustration and description.They are not intended to be exhaustive or to limit the invention to theprecise forms disclosed. Rather, it should be appreciated that manymodifications and variations are possible in view of the aboveteachings. The embodiments were chosen and described in order to bestexplain the principles of the invention and its practical applications,to thereby enable others skilled in the art to best utilize theinvention and various embodiments with various modifications as aresuited to the particular use contemplated.

What is claimed is:
 1. A device, comprising: a transmitter having anoutput configured to be coupled with a wired link; and control logiccoupled to the transmitter, wherein the control logic is configured to:enable the transmitter to communicate information over the wired link toa second device at an initial data rate; increase a data rate ofcommunication of information by the transmitter over the wired link tothe second device relative to the initial data rate of communication ofinformation by the transmitter to the second device, wherein theincreased data rate is a non-integer multiple of the initial data rate;determine, for the increased data rate, a metric corresponding tocommunication of the information by the transmitter over the wired linkto the second device; and adjust, in response to the determination ofthe metric corresponding to communication of the information over thewired link, at least one of a voltage swing of the transmitter output ora supply voltage.
 2. The device of claim 1, wherein the control logic isconfigured to use an iterative process in which the data rate ofcommunication of information over the wired link by the transmitter tothe second device is increased until a measured voltage margincorresponds to an error rate that is greater than a predetermined errorrate.
 3. The device of claim 2, wherein the control logic is furtherconfigured to determine a range of data rates, and wherein the range ofdata rates includes at least one data rate greater than the initial datarate, and corresponds to error rates that do not exceed thepredetermined error rate.
 4. The device of claim 2, wherein theincreased data rate is less than a maximum data rate that corresponds toan error rate greater than the predetermined error rate.
 5. The deviceof claim 1, wherein a ratio of the increased data rate and the initialdata rate is greater than one and less than two.
 6. The device of claim1, wherein data included in a baseband signal transmitted by thetransmitter over the wired link to the second device includes amplitudemodulated data.
 7. The device of claim 1, wherein the increased datarate is less than a target data rate, and the control logic isconfigured to increase the at least one of the voltage swing of thetransmitter output or the supply voltage.
 8. The device of claim 1,wherein the increased data rate is greater than a target data rate, andthe control logic is configured to decrease the at least one of thevoltage swing of the transmitter output or the supply voltage.
 9. Thedevice of claim 1, wherein the supply voltage is for one of a phaselocked loop circuit of the device or the transmitter.
 10. The device ofclaim 1, further including a fractional-N phase locked loop circuit togenerate a clock signal provided to the transmitter.
 11. A method foroperating a transmitter coupled with a wired link, comprising: at adevice having the transmitter: using the transmitter, transmittinginformation over the wired link to a second device at an initial datarate of communication of information; using the transmitter,transmitting information over the wired link to the second device at anincreased data rate of communication of information, wherein theincreased data rate is higher than the initial data rate, wherein theincreased data rate is a non-integer multiple of the initial data rate;determining, for the increased data rate, a metric corresponding tocommunication of the information over the wired link to the seconddevice; and adjusting, in response to the determination of the metriccorresponding to communication of the information over the wired link tothe second device, at least one of a voltage swing of the transmitteroutput or a supply voltage.
 12. The method of claim 11, wherein the datarate of communication of information over the wired link by thetransmitter to the second device is increased iteratively until ameasured voltage margin corresponds to an error rate that is greaterthan a predetermined error rate.
 13. The method of claim 12, includingdetermining a range of data rates, wherein the range of data ratesincludes at least one data rate greater than the initial data rate, andcorresponds to error rates that do not exceed the predetermined errorrate.
 14. The method of claim 12, wherein the increased data rate isless than a maximum data rate that corresponds to an error rate greaterthan the predetermined error rate.
 15. The method of claim 11, wherein aratio of the increased data rate and the initial data rate is greaterthan one and less than two.
 16. The method of claim 11, wherein dataincluded in a baseband signal transmitted by the transmitter over thewired line to the second device includes amplitude modulated data. 17.The method of claim 11, wherein the increased data rate is less than atarget data rate, and the adjusting includes increasing the at least oneof the voltage swing of the transmitter output or the supply voltage.18. The method of claim 11, wherein the increased data rate is greaterthan a target data rate, and the adjusting includes decreasing the atleast one of the voltage swing of the transmitter output or the supplyvoltage.
 19. The method of claim 11, wherein the supply voltage is forone of a phase locked loop circuit of the device or the transmitter. 20.A device, comprising: transmit means for coupling an output of thedevice to a wired link; and control means, coupled to the transmitmeans, for controlling operation of the transmit means, wherein thecontrol means is configured to: enable the transmit means to communicateinformation over the wired link to a second device at an initial datarate; increase a data rate of communication of information by thetransmit means over the wired link to the second device relative to theinitial data rate of communication of information by the transmit meansto the second device, wherein the increased data rate is a non-integermultiple of the initial data rate; determine, for the increased datarate, a metric corresponding to communication of the information by thetransmit means over the wired link to the second device; and adjust, inresponse to the determination of the metric corresponding tocommunication of the information over the wired link, at least one of avoltage swing of the transmit means or a supply voltage.